Research Article  Open Access
Kanawat Nuangwongsa, Chuwong Phongcharoenpanich, "Design of Symmetrical Beam TripleAperture Waveguide Antenna for Primary Feed of Reflector", International Journal of Antennas and Propagation, vol. 2016, Article ID 5830527, 14 pages, 2016. https://doi.org/10.1155/2016/5830527
Design of Symmetrical Beam TripleAperture Waveguide Antenna for Primary Feed of Reflector
Abstract
This research presents a tripleaperture waveguide antenna as the primary feed of parabolic reflectors. The proposed antenna is able to rectify the asymmetry and also achieve a symmetrical unidirectional beam through the application of two parasitic coupling apertures. The design of the antenna is that of a rectangular waveguide (radiating aperture) vertically jointed to the two coupling apertures of the same measurement widthwise (i.e., one stacked on top and the other underneath) to achieve the symmetrical beam. The rectangular waveguide is 97.60 mm and 46.80 mm in width () and height (), respectively, to propagate the WLAN frequency band of 2.412–2.484 GHz. Simulations were carried out to determine the optimal antenna parameters and an antenna prototype was subsequently fabricated and tested. The simulated beamwidths in the  and planes at dB were equally 67° (i.e., 67° for both the  and planes) and at dB also equally 137°, while the measured results at dB were equally 65° and at dB equally 135°. The simulation and measured results are thus in good agreement. The simulated and measured antenna gains are, respectively, 8.25 dBi and 9.17 dBi. The findings validate the applicability of the antenna as the prime feed for rotationally symmetric parabolic reflectors.
1. Introduction
In recent decades, the pointtopoint communications systems have rapidly advanced and become one of the brightest areas of the communications business [1]. Specifically, the pointtopoint links between hosts and clients are required in several wireless systems for communication over long distances, such as the microwave radio relay link, long length WiFi, wireless WAN/LAN link, satellite communication, and home satellite television [2].
Horn antennas, which are a principal component of the pointtopoint communication systems, were first developed nearly a century ago for military and scientific purposes but were not widely adopted until World War II. Typical horn antennas are of either rectangular or conical structures. The rectangular structure can further be divided into the plane, plane, and pyramidal horn structures [3, 4].
To enhance the performance of the pointtopoint communication requires a narrowbeam antenna with high gain [5], and one possible method to achieve the narrow beam is through a parabolic metal reflector antenna. In addition, the feeding point of the parabolic reflector should be located at the reflector focus to generate the narrow beam (i.e., pencil beam). In [6], the authors reviewed publications on the pointtopoint communication and documented that the generation of the pencil beam requires an antenna with symmetrical beam as the primary feed.
The radiation pattern of a parabolic reflector (secondary antenna) typically corresponds to that of the primary feed antenna. In other words, the asymmetric radiation pattern from the primary feed contributes to the asymmetrical incidence of the secondary antenna and vice versa [7]. In fact, it is difficult to obtain the symmetrical radiation pattern at the primary feed due to the beamwidth asymmetry between the  and planes [8].
To address the asymmetry issue, several antenna structures have been proposed. In [9], a pyramidal horn antenna was utilized to obtain the symmetric radiation patterns in the  and planes; nevertheless, the antenna structure was large with the width, height, and length of , , and . In [10], the author experimented with a diagonal horn antenna with very low crosspolarization and axially symmetrical field distribution at the horn aperture; however, the antenna has a large aperture size of and in width and height.
Generally, the corrugated horn consisting of parallel slots or grooves can create a hybridmode pattern in the aperture which straightens out the electric field and reduces diffractions from the edge [11, 12]. In [13–18], the conical corrugated horn antennas were utilized to generate the symmetrical beam with high gain and low side lobe level. The antennas structures are however complicated. On the contrary, for the typical rectangular corrugated horn antenna structure, the slots or grooves are located inside both vertical and horizontal planes around the rectangular aperture area. The rectangular corrugated horn [19] was experimented and it was reported that this antenna type failed to generate the symmetrical beam despite its relatively large size. In [20], the authors proposed a flared rectangular horn corrugated along the plane flaring walls to achieve the symmetry in the  and planes; nevertheless, the antenna construction is very complicated and the antenna aperture is considerably large. For the rectangular waveguide aperture perpendicular to the direction, the diffracted wave is almost in plane and it is minimal in plane. The parasitic coupling apertures are proposed to locate in plane (vertical plane) outside the radiating aperture. One aperture is stacked on top (top section) and the other is stacked underneath (bottom section) the radiating rectangular waveguide (middle section). This makes the proposed tripleaperture waveguide antenna less complicated and easy fabricated compared to the typical corrugated horn antenna.
This research has thus proposed a tripleaperture waveguide antenna as the primary feed of a parabolic reflector. The antenna can achieve a symmetrical unidirectional beam through the use of two parasitic coupling apertures. In fact, an independent use of an openended rectangular waveguide as the primary feed of a parabolic reflector is rare due to the asymmetry and low directivity [21]. The proposed antenna design consists of a rectangular radiating waveguide jointed to the two coupling apertures, one stacked on top and the other underneath. In this research, the rectangular waveguide is 97.60 mm and 46.80 mm in width () and height (), respectively, to propagate the WLAN frequency band of 2.412–2.484 GHz. The proposed antenna is for pointtopoint communication and thus requires a front feed parabolic reflector [5, 22, 23] and is appropriate for WLAN applications along IEEE 802.11b/g/n. Moreover, the technique of coupling apertures can be applied to other frequency ranges by adjusting the antenna electrical size.
The organization of the research is as follows: Section 1 is the introduction. Section 2 describes the design of the proposed tripleaperture waveguide antenna, while Section 3 discusses the parametric study and the simulation results of the antenna. Section 4 deals with the antenna prototype and the experimental results. The concluding remarks are provided in Section 5.
2. The Antenna Design
The structure of the tripleaperture waveguide antenna, as the name implies, is made up of one radiating section and two coupling sections. The configuration of the proposed antenna is illustrated in Figure 1, in which the radiating aperture is the middle section with the width and height of and , while the two coupling apertures refer to those on top and underneath the radiating aperture, with the width, height, and length of , , and . The width ( mm) and height ( mm) of the rectangular waveguide (the middle section) are fixed, where the relationship between its width () and length () is that of , to achieve the center frequency of 2.45 GHz in the dominant mode () [24–28].
Inside the middle section (the radiating section) is mounted a linear electric probe at a distance of from its closed end () along the direction with the axial axis propagation. The height of linear electric probe () is . The inclusion of both parasitic coupling apertures on the vertical plane at the open end is to reduce the diffraction field and achieve symmetry.
In this research, the initial length of the radiating section () is because the standing wave pattern is repeated every . Therefore, the distance between the maximum and minimum electric field distributions is and the entire length of the radiating section () is approximately so as to realize the maximum electric field density at the aperture, as shown in Figure 2. The length of the rectangular radiating waveguide () is thus 152.40 mm [29].
3. Parametric Study and Simulation Results
3.1. The Antenna without Parasitic Coupling Apertures
Under this scenario, simulations were carried out on a waveguide without the parasitic coupling apertures using CST Microwave Studio. The waveguide is of rectangular shape, where the relationship between its width () and length () is that of . In addition, the waveguide is of aluminum material and 2 mm in thickness. Inside the waveguide is an electric probe that is connected to a 50 Ω Ntype connector. The width () and length () of the rectangular waveguide are capable of achieving the resonant frequency () at the center frequency of 2.45 GHz. Table 1 tabulates the physical and electrical sizes of the rectangular waveguide (i.e., the antenna without the coupling apertures).

Figure 3 illustrates the simulated electric field distribution at the center of the width () side of the antenna without the parasitic coupling apertures at the 2.45 GHz frequency. It is found that the distribution travels in the direction and that the diffraction grows stronger around the edges of the waveguide (the plane). On the other hand, the diffraction on the plane is minimal. The plane phenomenon contributes to the asymmetry between the  and plane radiations.
Figures 4 and 5, respectively, depict the simulated and gain as well as the input impedance of the antenna without the parasitic coupling apertures. As illustrated in the figures, in the absence of the coupling apertures, the antenna gain (6.70 dBi) is relatively low despite the fairly satisfactory input impedance ( Ω) and dB.
In Figure 6, the simulated beamwidths at dB and dB in the plane, respectively, are 106° and 270° and in the plane are 65° and 110°. Since the principle application of the proposed tripleaperture waveguide antenna is the primary feed of a parabolic reflector, this research has thus taken into account the beamwidth at dB. As illustrated in Figure 6, the radiation patterns of the antenna without the parasitic coupling apertures in the  and planes are asymmetrical.
(a)
(b)
3.2. The Antenna with Parasitic Coupling Apertures
To rectify the asymmetry, two parasitic coupling apertures are incorporated with the rectangular waveguide whereby one aperture is stacked on top (top section) and the other underneath (bottom section) the radiating waveguide (middle section). To achieve the resonant frequency at the center frequency of 2.45 GHz, this research has utilized the TE_{101} mode to determine the length () and height () of the parasitic coupling apertures [28, 29] while its width () is identical to that of the radiating rectangular waveguide (97.60 mm). Simulations were then carried out using CST Microwave Studio and the optimal simulation results for the waveguide antenna with the parasitic coupling apertures are tabulated in Table 2. The realization of the target resonant frequency is largely subject to and .

Figure 7 illustrates the simulated electric field distribution of the waveguide antenna with the parasitic coupling apertures at the center of the width () side. It is found that the wave diffraction is reduced with the use of the coupling apertures (the top and bottom shorter sections) in conjunction with the radiating waveguide (the middle section).
3.2.1. Impedance Bandwidth for Various Antenna Parameters
Figure 8 depicts the simulated dB for various rectangular waveguide lengths () and at the simulated resonates at the center frequency of 2.45 GHz. Figure 9 illustrates the simulated dB for various electric probe heights () and the results indicate the optimal height of the probe () of . In Figure 10, the simulated for various distances between the probe and the closed end of the radiating waveguide () reveal that the optimal distance that achieves the resonance at the target center frequency is .
Figure 11 illustrates the simulated of the proposed waveguide antenna for various heights () of the coupling aperture, which were varied between and . The results indicate that exerts little influence over and the optimal coupling aperture height () is , at which the beamwidths at dB and dB in both the  and planes are symmetrical. This confirms that the utilization of the coupling apertures contributes to the reduction of the diffraction field at the edges of the radiating waveguide. Figure 12 depicts the simulated for various lengths of the coupling aperture () and the results show that vary considerably with the variation in . The resonant frequency is however achieved at of .
3.2.2. Radiation Patterns for Various Heights of the Parasitic Coupling Apertures ()
Figures 13–15, respectively, illustrate the simulated radiation patterns for various heights of the parasitic coupling apertures () in the  and planes at the lower, center, and upper frequencies of 2.412, 2.45, and 2.484 GHz, where was varied between and . Interestingly, in the plane, the beamwidths at dB (HPBW) and dB for the three frequencies exhibit slight differences. On the other hand, those in the plane for the aperture heights () between and are noticeably wider than the corresponding beamwidths for the three frequencies in the plane. For of and , the beamwidths at both dB and dB in both planes at the three frequencies are symmetrical. Thus, the coupling aperture height of is selected due to the smallest crosssectional area with the symmetrical radiation pattern. Table 3 tabulates the beamwidths at dB (HPBW) and dB for the three frequencies in the  and planes for the various heights of the parasitic coupling apertures ().

(a)
(b)
(a)
(b)
(a)
(b)
3.2.3. Radiation Patterns for Various Lengths of the Parasitic Coupling Apertures ()
Figures 16–18, respectively, illustrate the simulated radiation patterns for various lengths of the parasitic coupling apertures () in the  and planes at the lower, center, and upper frequencies of 2.412, 2.45, and 2.484 GHz, where was varied between and . It is found that at of the symmetry in both planes for the beamwidths at dB and dB is achieved. Table 4 tabulates the beamwidths at dB (HPBW) and dB for the three frequencies in the  and planes for the various lengths of the parasitic coupling apertures ().

(a)
(b)
(a)
(b)
(a)
(b)
Table 5 compares the simulated dB and dB beamwidths of the proposed antenna with and without the parasitic couplings apertures at the frequencies of 2.412, 2.45, and 2.484 GHz. Without the coupling apertures, the beamwidths at dB and dB in the plane and those in the plane for the three frequencies are dissimilar; in other words, the incidence of asymmetry is observed. Nevertheless, with the parasitic coupling apertures on top and underneath the width () side of the radiating rectangular waveguide, the dB and dB beamwidths in both planes for the three frequencies become symmetrical.

Figure 19 depicts the simulated antenna gains for various parasitic coupling aperture heights (). For , the antenna gains are relatively similar for the entire WLAN frequency range. The aperture height () of is thus selected for the smallest crosssectional area with symmetrical pattern. Figure 20 illustrates the simulated input impedance of the proposed antenna with the coupling apertures. The input impedance () at the center frequency of 2.45 GHz is Ω.
When comparing the proposed tripleaperture waveguide antenna with the conventional pyramidal horn antenna, it is obvious that the proposed antenna possesses smaller total antenna length. The length of the probefed waveguide must be appropriately designed to achieve the acceptable impedance matching [30]. The total length of the horn antenna is composed of the length of horn aperture and waveguide feeder. However, the radiating aperture and waveguide feeder of the proposed antenna are integrated into single structure. Therefore, the proposed antenna requires smaller total length to achieve the acceptable impedance matching. For instance, the total length of the conventional pyramidal horn antenna is 18.5% larger than that of the proposed antenna structure with the same radiating aperture and antenna gain. In addition, the proposed tripleaperture waveguide antenna has 11dB lower crosspolarization level than the conventional pyramidal horn antenna with the same antenna size. The reason is that the larger width of the pyramidal horn causes the higher horizontal electric field component.
4. Experimental Results
Figure 21 presents photographs of the prototype of the proposed tripleaperture waveguide antenna. The proposed antenna is operable in the 2.30–2.60 frequency range (12.245%), which also covers the WLAN frequency, for dB. The antenna prototype was fashioned from aluminum of 2 mm in thickness. The radiation pattern of the prototype antenna is symmetrical with unidirectional pattern, rendering it appropriate for use in the front feeding parabolic reflector in the pointtopoint communication.
(a)
(b)
(c)
Figure 22 compares the simulated and measured of the waveguide antenna with the parasitic coupling apertures. The simulation and measured results show the operating range of the antenna of 2.28–2.80 GHz and 2.30–2.60 GHz, respectively, indicating their good agreement.
Figure 23 compares the simulated and measured beamwidths at 2.45 GHz in the  and planes. Meanwhile, Table 6 tabulates the dB and dB beamwidths in both planes for the three frequencies. In Figure 24, the simulation antenna gain in front of the antenna at 0° is compared against the measured gain. The proposed antenna could achieve the maximum gain of 9.17 dBi at the WLAN center frequency.

(a)
(b)
5. Conclusion
This research has proposed the tripleaperture waveguide antenna as the primary feed of parabolic reflectors. The antenna could rectify the asymmetry and achieve the symmetrical unidirectional beam with the incorporation of two parasitic coupling apertures. The antenna consists of the radiating rectangular waveguide vertically jointed to the two coupling apertures to achieve the symmetrical beam. The rectangular waveguide is 97.60 mm and 46.80 mm in width () and height (), respectively, to propagate the WLAN frequency band of 2.412–2.484 GHz. In this research, the CST Microwave Studio program was deployed in simulation to determine the optimal antenna parameters and an antenna prototype was subsequently fashioned and experimented. The simulated beamwidths in the  and planes at dB were equally 67° and at dB equally 137°, while the measured beamwidths at dB were equally 65° and at dB equally 135° in the  and planes. The simulation and measured results are in good agreement. The simulated and measured antenna gains are, respectively, 8.25 dBi and 9.17 dBi. The findings confirm the applicability of the antenna as the prime feed for rotationally symmetric parabolic reflectors. In addition, the proposed antenna is light, inexpensive, and of low profile.
Competing Interests
The authors declare that there are no competing interests regarding the publication of this paper.
References
 P. S. Henry and H. Luo, “WiFi: what's next?” IEEE Communications Magazine, vol. 40, no. 12, pp. 66–72, 2002. View at: Publisher Site  Google Scholar
 K.L. Du and M. N. S. Swamy, Wireless Communication System: From RF Subsystems to 4G Enabling Technologies, Cambridge University Press, Cambridge, UK, 2010.
 C. A. Balanis, Antenna Theory Analysis and Design, John Wiley & Sons, New York, NY, USA, 1997.
 R. S. Elliott, Antenna Theory and Design, John Wiley & Sons, New York, NY, USA, 2003.
 R. Gardelli, G. La Cono, and M. Albani, “A lowcost suspended patch antenna for WLAN access points and pointtopoint links,” IEEE Antennas and Wireless Propagation Letters, vol. 3, no. 1, pp. 90–93, 2004. View at: Publisher Site  Google Scholar
 Z. N. Chen, X. Qing, T. S. P. See, and W. K. Toh, “Antennas for WiFi connectivity,” Proceedings of the IEEE, vol. 100, no. 7, pp. 2322–2329, 2012. View at: Publisher Site  Google Scholar
 V. F. Fusco, Foundations of Antenna Theory and Techniques, Pearson Education, The Queens University of Belfast, 2007.
 S. Rao, L. Shafai, and S. Sharma, Handbook of Reflector Antennas and Feed Systems. Volume 3: Applications of Reflectors, Artech House, Norwood, Mass, USA, 2013.
 K.R. Chou, T.D. Wu, H.N. Lin, T.S. Liao, and K.K. Tiong, “Design and simulation of a Cband pyramidal horn antenna for waterlevel radar sensors,” Journal of Marine Science and Technology, vol. 23, no. 2, pp. 220–224, 2015. View at: Publisher Site  Google Scholar
 O. Xu, “Diagonal horn gaussian efficiency enhancement by dielectric loading for submillimeter wave application at 150 GHz,” Progress in Electromagnetics Research, vol. 114, pp. 177–194, 2011. View at: Publisher Site  Google Scholar
 R. C. Johnson, Antenna Engineering Handbook, Georgia Institute of Technology, Atlanta, Ga, USA; McGrawHill, New York, NY, USA, 1993.
 P. J. B. Clarricoats and A. D. Olver, Corrugated Horns for Microwave Antenna, vol. 18 of Electromagnetic Waves, Perter Peregrinus, 1984.
 M. V. Gohil, B. J. Makwana, and R. B. Ambaliya, “Corrugated horn antennas: a review,” International Journal of Advanced Technology & Engineering Research (IJATER), vol. 4, no. 2, pp. 27–29, 2014. View at: Google Scholar
 T. Salimi, A. Maghoul, and A. A. Abbasid, “Design of a compact Gaussian profiled corrugated horn antenna for low sidelobelevel applications,” International Journal of Computer Theory and Engineering, vol. 5, no. 2, pp. 223–226, 2013. View at: Publisher Site  Google Scholar
 J. E. McKay, D. A. Robertson, P. A. S. Cruickshank et al., “Compact Wideband corrugated feedhorns with ultralow sidelobes for very high performance antennas and quasioptical systems,” IEEE Transactions on Antennas and Propagation, vol. 61, no. 4, pp. 1714–1721, 2013. View at: Publisher Site  Google Scholar
 J. Teniente, R. Gonzalo, C. del Rio et al., “Corrugated horn antenna for lowpower testing of the quasioptical transmission lines at TJII stellerator,” International Journal of Infrared and Millimeter Waves, vol. 20, no. 10, pp. 1757–1767, 1999. View at: Publisher Site  Google Scholar
 J. Teniente, R. Gonzalo, and C. delRío, “Innovative highgain corrugated horn antenna combining horizontal and vertical corrugations,” IEEE Antennas and Wireless Propagation Letters, vol. 5, no. 1, pp. 380–383, 2006. View at: Publisher Site  Google Scholar
 J. Teniente, A. Martínez, B. Larumbe, A. Ibáñez, and R. Gonzalo, “Design guidelines of horn antennas that combine horizontal and vertical corrugations for satellite communications,” IEEE Transactions on Antennas and Propagation, vol. 63, no. 4, pp. 1314–1323, 2015. View at: Publisher Site  Google Scholar  MathSciNet
 M. Bersanelli, M. Bensadoun, G. De Amici et al., “Construction technique and performance of a 2 GHz rectangular corrugated horn,” IEEE Transactions on Antennas and Propagation, vol. 40, no. 9, pp. 1107–1109, 1992. View at: Publisher Site  Google Scholar
 A. I. Zaghloul and T. Anthony, “Eplane flared rectangular corrugated horn for tapered aperture,” in Proceedings of the IEEE International Symposium on Antennas and Propagation and USNC/URSI National Radio Science Meeting (APSURSI '08), pp. 1–4, San Diego, Calif, USA, July 2008. View at: Publisher Site  Google Scholar
 R. E. Collin, Field Theory of Guided Waves, IEEE Press, Piscastaway, NJ, USA, 2nd edition, 1992.
 J.M. Lee and J.M. Woo, “Design of array synthesis horn antenna for high power microwave applications,” in Proceedings of the PIERS, Moscow, Russia, August 2012. View at: Google Scholar
 R. Jordan and C. T. Abdallah, “Wireless communications and networking: an overview,” IEEE Antennas and Propagation Magazine, vol. 44, no. 1, pp. 185–193, 2002. View at: Publisher Site  Google Scholar
 K. Saeed, R. D. Pollard, and I. C. Hunter, “Substrate integrated waveguide cavity resonators for complex permittivity characterization of materials,” IEEE Transactions on Microwave Theory and Techniques, vol. 56, no. 10, pp. 2340–2347, 2008. View at: Publisher Site  Google Scholar
 Y. Li and J. Papapolymerou, “A novel highQ cavity resonator for reconfigurable WPAN applications at 60 GHz,” in Proceedings of the 39th European Microwave Conference, Rome, Italy, 2009. View at: Google Scholar
 S. Adhikari, Y.J. Ban, and K. Wu, “Magnetically tunable ferrite loaded substrate integrated waveguide cavity resonator,” IEEE Microwave and Wireless Components Letters, vol. 21, no. 3, pp. 139–141, 2011. View at: Publisher Site  Google Scholar
 D.A. Srimoon, C. Phongcharoenpanich, and M. Krairiksh, “Probefed rectangular ring antenna with a crossstrip for low crosspolarization,” IEEE Transactions on Antennas and Propagation, vol. 54, no. 5, pp. 1586–1591, 2006. View at: Publisher Site  Google Scholar
 M. Miao and C. Nguyen, “A novel multilayer aperturecoupled cavity resonator for millimeterwave CMOS RFICs,” IEEE Transactions on Microwave Theory and Techniques, vol. 55, no. 4, pp. 783–787, 2007. View at: Publisher Site  Google Scholar
 T. Moreno, Microwave Transmission Design Data by Theodore Moreno, 1948.
 W. W. S. Lee and E. K. N. Yung, “The input impedance of a coaxial line fed probe in a cylindrical waveguide,” IEEE Transactions on Microwave Theory and Techniques, vol. 42, no. 8, pp. 1468–1473, 1994. View at: Publisher Site  Google Scholar
Copyright
Copyright © 2016 Kanawat Nuangwongsa and Chuwong Phongcharoenpanich. This is an open access article distributed under the Creative Commons Attribution License, which permits unrestricted use, distribution, and reproduction in any medium, provided the original work is properly cited.